By Muhammed Bolatkale, Lucien J. Breems, Visit Amazon's Kofi A. A. Makinwa Page, search results, Learn about Author Central, Kofi A. A. Makinwa,
This publication describes recommendations for figuring out huge bandwidth (125MHz) over-sampled analog-to-digital converters (ADCs) in nano meter-CMOS methods. The authors provide a transparent and whole photograph of method point demanding situations and useful layout suggestions in high-speed Delta-Sigma modulators. Readers might be enabled to enforce ADCs as continuous-time delta-sigma (CT∆Σ) modulators, delivering easy resistive inputs, which don't require using power-hungry enter buffers, in addition to delivering inherent anti-aliasing, which simplifies process integration. The authors concentrate on the layout of excessive velocity and wide-bandwidth ΔΣMs that make a step in bandwidth variety which used to be formerly simply attainable with Nyquist converters. extra particularly, this publication describes the steadiness, energy potency and linearity limits of ΔΣMs, aiming at a GHz sampling frequency.
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Additional resources for High Speed and Wide Bandwidth Delta-Sigma ADCs
Sample text
2 Int. 5 GBW of the amplifier normalized to ωs=2*π*fs Fig. 2 Building-block specifications of the loop filter Block Sampling speed Input signal Loop filter Integrators OTA1 OTA2 OTA3 Specification fs Vi n Input impedance Phase margin Total harmonic distortion (THD) Phase shift DC gain (ADC ) GBW HD3 Vnoise DC gain (ADC ) GBW Vnoise gm HD3 Value 4 GHz 2Vp p 1k 80ı @0:5fs 80 dBc 90ı @0:5fs >35 dB 8 GHz 80 dBc 80 dBc >35 dB 6 GHz 80 dBc 0:5 –2 tunable 30 dBc integrators require an approximate phase shift of 90ı at 0:5fs .
11), the HD3 tone is proportional to ˇ and for ˇ > 0:1 the SNDR also starts reducing, which implies that self mixing of the quantization noise due to the non-linear integrator increases the in-band noise of the modulator. 1. Based on the system-level simulations, the SNR of the loop filter (SNRLF ) is set to 80 dB. Both the input impedance of the first integrator and its amplifier contribute to the noise. For a differential implementation, the SNRLF is expressed as: SNRLF D 10 log10 ! 13) where v2n;Ri n D 4kTRi n BW , v2n;amp D 4kTReq BW , and Req D 2=3gm [13].
The output of the last integrator acts as the output of the loop filter thus driving the quantizer. 5 Normalized frequency (f/fs) [−] Fig. 5 fp (Hz) x 109 Fig. 5 z-tp (dac) z-tp (q) ELDdac ELDq Fig. 9 shows the SQNR loss as a function of the ADC of the last integrator’s amplifier shown in Fig. 8. Due to the limited DC gain of the amplifier, the SQNR reduces. 10a shows the maximum output of the integrator stages. The output of the first and the second integrator increases while the feedback of the modulator keeps the output of the loop filter at the same level when compared to the ideal implementation.
